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BW6562A high pfc led driver ?2012 bruckewell technology corp., ltd. 1 www.bruckewell - semi.com/ features ? single stage fly - back controller with pfc ? transition - mode operation ? ultra - low start - up current ? internal start - up timer ? low operating supply current ? low quiescent current ? disable function on error amplifier ( e/a ) input ? totem pole, push - pull output drive ? adjustable output over - voltage protection ? under - voltage lockout with hysteresis ? 1% precision internal reference voltage typical applications ? fly - back power converters ? pfc pre - regulators to meet iec61000 - 3 - 2 ? hi - end ac - dc adapter/charger ? electronic s ingle stage led driver ? electronic ballast product description the BW6562A is a cost effective high performance transition - mode (tm) power factor correction (pfc) controller ic optimized for high pfc led driver, battery chargers and pre - regulator applicatio ns. the BW6562A integrates an internal start - up timer, a highly linear multiplier with t otal h armonics d istortion (thd) optimizer for near unity power factor, a z ero c urrent d etector (zcd) to ensure transition - mode operation and a current sensing comparato r with built - in leading edge blanking. with zcd control, power mosfet is always turned on with zero inductor current. consequently, transition - mode control achieves lower switching loss and reduced noise. the BW6562A offers great protection coverage inclu ding system accurate adjustable over - voltage protection (ovp), input under - voltage lockout (uvlo), multiplier output clamp and gd output clamp for external power mosfet protection. the totem pole output stage is capable of delivering sink/source drive cur rent of +800ma/ - 600ma. the BW6562A is available in sop - 8 package. typical application circuit
BW6562A high pfc led driver ?2012 bruckewell techn ology corp., ltd. 2 www.bruckewell - semi.com/ pin assignments and ordering information device packaging quantity of tape & reel BW6562A mst sop - 8 3000 pin descriptions pin no. pin name functio n inverting input pin of the error amplifier. 1 inv the information on the output voltage of the pfc controller is fed into this pin through a resistor divider. the pin can also be used as chip enable/disable control pin. output pin of the erro r amplifier. 2 comp a compensation network is placed between this pin and inv to achieve stability of the voltage control loop and ensure high power factor and low thd. main input to the multiplier. 3 mult this pin is connected to the rectified mains volta ge via a resistor divider and provides the sinusoidal reference to the current loop. current sense i nput pin to the internal pwm comparator. 4 cs the current flowing in the mosfet is sensed through a resistor; the resulting voltage is applied to this p in and compared with an internal sinusoidal - shaped reference, generated by the multiplier, to switch on or off the external mosfet. the pin is equipped with 200ns leading - edge blanking for improved noise immunity. zero current detection pin. 5 zcd boos t inductors demagnetization sensing input for transition - mode operation. a negative - going edge triggers mosfets turn - on. g round pin. 6 gnd current return for both the signal part of the ic and the gate driver. gate driver output pin. 7 g d the tot em pole output stage is able to drive power mosfet s with a peak current of 600ma source and 800ma sink. the high - level voltage of this pin is clamped at about 12v to avoid excessive gate voltages in case the pin is supplied with a high v cc . system power input pin. 8 v cc supply voltage of both the signal part of the ic and the gate driver. upper limit is extended to a maximum of 32 v to provide a more headroom for supply voltage changes. this pin has an internal 34 v (min.) zener diode to protect the ic i tself from over - voltage transients.
BW6562A high pfc led driver ?2012 bruckewell techn ology corp., ltd. 3 www.bruckewell - semi.com/ absolute maximum ratings ( note 1) symbol parameter ratings unit v cc ic supply voltage - 0.3 ~ + 40 v i gd output totem p ole peak current - 600 (sour ce) / + 800 (sink) ma * ( note 2) analog inputs & outputs - 0.3 ~ +8 .0 v i zcd zero current detector max imum current ?0 ma continuous power dissipation (t a +25c) 8 pin sop (de - rat ing 6.3mw/c above +25c) 0. 63 w t j junction temperature +1 50 ? t st g storage temperature range - 65 ~ + 150 ? ja junction - to - ambient thermal resistance 165 ? /w note 1. exceeding these ratings could cause damage to the device. all voltages are with respect to ground. currents are positive into, negative out of the specified terminal . 2. * : pin 1 (inv), pin 2 (comp), pin 3 (mult), pin 4 (cs) recommended operating conditions symbol parametar min. max. unit v cc dc input supply voltage range, v cc to gnd 10.5 32 v v inv inv input pin voltage range relative to gnd 2.455 2.545 v v mult mult input pin voltage rang e relative to gnd 0 3 v v cs cs input pin voltage range relative to gnd 0 1.2 v t a ambient temperature range (note 3) - 40 +85 ? note : 3. maximum ambient temperature range is limited by allowable power dissipation.
BW6562A high pfc led driver ?2012 bruckewell techn ology corp., ltd. 4 www.bruckewell - semi.com/ electrical characteristics (over reco mmended operating conditions unless otherwise specified. v cc 12v, t j - 25c ~ +125c, c o 1nf) parameter symbol min. typ. max. unit condition s upply v oltage operating range v cc 10.5 32 v after turn - on turn - on threshold v cc ( on ) 11.7 12.5 13.3 v turn - off threshold v cc ( off ) 8.7 9.0 9.3 v hysteresis v cc 3.0 4.0 v zener voltage v z 34 38 v i cc 20ma s upply c urrent start - up current i start 30 60 a before turn - on, v cc 11v quiescent current i q 2.50 3.75 ma after turn on operating supply current i cc 3.5 5.0 ma 70khz quiescent current i q(ovp) 1.7 2.2 ma during ovp, or v inv 150mv e rror a mplifier voltage feedback input threshold v inv 2.455 2.500 2.5 4 5 v 10.5v < v cc < 32 v line regulation v line 2 5 mv v cc 10.5v ~ 32 v input bias current i inv - 1 a v inv 0v ~ 3v voltage gain g v 60 80 db open loop gain - bandwidth product gb 1 mhz source current i comp(source) - 2.0 - 3.5 - 5 .0 ma v comp 4v, v inv 2.4v sink current i comp(sink) 2.4 4.5 ma v comp 4v, v inv 2.6v upper clamp voltage v comp(up) 5.3 5.7 6 .0 v i source 0.5ma lower clamp voltage v comp(low) 2.10 2.25 2.40 v i sink 0.5ma dis able threshold v inv(dis) 150 200 250 mv re - start threshold v inv(en) 380 450 520 mv m ultiplier i nput input bias current i mult - 1 a v mult 0v ~ 4v linear operation range v mult 0 ~ 3 v output max. slope v cs /v mult 1.0 1.1 v/v v mult 0v ~ 1v, v comp upper clamp gain ( note 4 ) k 0.32 0.38 0.44 v v mult 1v, v comp 4v z ero c urrent d etector upper clamp voltage v zcdh 5.0 5.7 6.5 v i zcd 2.5ma lower clamp voltage v zcdl - 0.3 0 0.3 v i zcd - 2.5ma arming voltage ( note 5 ) v zcda 1.4 v positive - going edge
BW6562A high pfc led driver ?2012 bruckewell techn ology corp., ltd. 5 www.bruckewell - semi.com/ electrical characteristics (continued) (over recommended operating conditions unless otherwise specifi ed. v cc 12v, t j - 25c ~ +125c, c o 1nf) parameter symbol min. typ. max. unit condition triggering voltage ( note 5 ) v zcdt 0.7 v negative - going edge input bias current i zcdb 2 a v zcd 1 .0v ~ 4.5v source current capability i zcd(source) - 2.5 ma sink current capability i zcd(sink) 2.5 ma o utput o ver - v oltage dynamic ovp triggering current i ovp 27 a hysteresis ( note 5 ) i ovp 20 a static ovp threshold v ovp(th) 2.10 2.25 2.40 v c urrent s ense c omparator input bias current i cs - 1 a v cs 0 v leading edge blanking t leb 100 200 300 ns delay to output t d(h - l) 175 ns current sense clamp v cs 1 .00 1.08 1.16 v v comp u pper clamp, v mult 1.5v v cs(o s_0v ) 25 v mult 0 v current sense offset v cs(o s_2.5v ) 5 mv v mult 2.5v starter start timer period t start 75 19 0 300 s gate d river output low voltage v ol 0.6 1.2 v i sink 100 ma output high voltage v oh 9.8 10.3 v i source 5 ma peak source current i source(pk) - 0.6 a peak sink current i sink(pk) 0.8 a voltage fal l time t f all 30 70 ns voltage rise time t r ise 60 110 ns output clamp voltage v o(clamp) 10 12 15 v i s ource 5 ma, v cc 20v uvlo saturation v uvlo(sat) 1.1 v v cc 0v ~ v cc ( on ) , i sink 2 ma note 4 . the multiplier output is given by : v cs k v mult (v c omp 2.5) 5 . parameters guaranteed by design, functionality tested in production.
BW6562A high pfc led driver 2012 bruckewell techn ology corp., ltd. 6 www.bruckewell - semi.com/ functional block diagram applicat ion information operation overview the BW6562A is an excellent transition - mode power factor correction controller for ac - dc switching mode power supply applications. it meets the iec61000 - 3 - 2 requirement and is intended for the use in those applications th at demand low power harmonics distortion. it integrate s more functions to reduce the external components counts and the size. its major features are described as below. power factor correction and thd the BW6562A features a one linear multiplier with thd optimizer for near unity power factor. to explain pfc and thd relation. first, average power is defined by v rms i rms cos( ) (1) pf (7) (8) (9) to consider current h armonics effect, i rms is given by (10) where i sn is rms value of n - th input h armonics current. so, effective value of input distortion current is defined by
BW6562A high pfc led driver 2012 bruckewell techn ology corp., ltd. 7 www.bruckewell - semi.com/ where is phase shift between input voltage and curren t. effective value of input voltage and current are defined by as follows : (2) (3) where v s (t) is instantaneous value of input voltage, i s (t) is instantaneous value of input current, t is the cycle. therefore, p av is written as : avg [ v(t) i(t) ] ( 4) (5) and apparent power is defined by v rms i rms (6) where i rms is the root mean square (rms) value of i rms . therefore, based on the above equations, obtained power factor (pf) is defined by the ratio of average power and apparent power : i th (11) (12) to quantify degree of current wavefor m distortion, thd is written by thd (13) (14) so, pf (15) if the c urrent and voltage are in phase, then 0, which will lead to cos( ) 1, and the pf will be simplified as pf ( 16) based on the equation 16, if thd is very small, then it will get near unity power factor. the major cause of this thd distortion is the inability of the system to transfer energy effectively when the instantaneous line voltage is very low. this effe ct is magnified by the high - frequency filter capacitor placed after the bridge rectifier, which retains some residual voltage that causes t he diodes of the bridge rectifier to be reverse - biased and the input current flow to temporarily stop. to overcome t his issue, the circuit section designed in the BW6562A forces the pfc regulator to process more energy near the line voltage zero - crossings, as compared to that commanded by the control loop. this results in both, minimizing the time interval when energy t ransfer is lacking, and fully discharging the high - frequency filter capacitor after the bridge . the BW6562A is design ed with a special circuit that reduces the conduction dead - angle occurring to the ac is shown in typical application circuit on p age 1. during the start - up transient, the v c c is lower than the uvlo threshold voltage (v cc(on) ) thus there is no gate pulse produced from the BW6562A to drive power mosfet. therefore, the current through r 6 will provide the start - up current and to charge the capacitor c2. whenever the v cc voltage i s high enough to turn on the BW6562A and further to deliver the gate drive signal . once the BW6562A is in normal operation, the supply current is switched to and provided from the auxiliary winding of the pfc choke ( transformer). lower start - up current req uirement on the pfc controller will help to increase the value of r 6 and then reduce the power consumption on r 6 . by using cmos process and the special circuit design, the maximum start - up current of the BW6562A is only 6 0 a. if a higher resistance value of r 6 is chosen, it usually takes more time to start - up. to carefully select the value of r 6 and c 2 will optimize the power consumption and start - up time .
BW6562A high pfc led driver ?2012 bruckewell techn ology corp., ltd. 8 www.bruckewell - semi.com/ input c urrent near the zero - crossings of the line vol tage (crossover distortion). in this way the thd of the current is considerably reduced. the result will be near unity power factor. in essence, the circuit artificially increases the on t ime of the p ower s witch with a positive offset added to the output of the multiplier in the proximity of the line voltage zero - crossings. this offset is reduced as the instantaneous line voltage increases, so that it becomes negligible as the line voltage moves towards the peak of the sinusoidal waveform. therefore, to m aximize the benefit from the thd improvement circuit, the high - frequency filter capacitor after the bridge rectifier should be minimized, and kept just to satisfy the emi filtering requirements. under - voltage lockout an uvlo comparator is implemented in i t to detect the voltage on the v cc pin. it would assure the supply voltage enough to turn on the BW6562A pfc controller and further to drive the power mosfet. a hysteresis is built in to prevent the shutdown from the voltage dip during start up. the turn - o n and turn - off threshold level are set at 12. 5 v and 9 v, respectively. start - up current and start - up circuit the typical start - up circuit to generate the BW6562A v cc output voltage setting the BW6562A monitors the output voltage sign al at inv pin through a resistor divider pair r 3 and r 4 . a trans - conductance amplifier is used instead of the conventional voltage amplifier. th is trans - conductance amplifie r (voltage controlled current source) also provides the additional ovp function. ne glecting ripple current, current flowing through r3, i r3 , will equal to current through r4, i r4 , as the non - inverting input of the error amplifier is biased inside the BW6562A at 2.5v , a nd output voltage is determined by the following relationship. i r4 i r3 (17) where r3 and r4 are top and bottom feedback resistor values (as shown in the typical applic ation circuit on page 1 ). i f any abrupt change of output voltage, v o > 0, occurs due to a load drop, the voltage at pin inv will be kept at 2.5v by the local feedback of the ea, the network connected between inv and comp would introduces a time constant to achieve high pf. the curr ent through r4 will remain equal to 2.5/r4 but i r3 will become : i' r3 (18) the extra current i r3 will flow through the compensation network and enter the err or amplifier output via pin comp . w hen it reaches about 37 a, the output voltage of the multiplier is forced to decrease which will reduce the energy drawn from the mains. t his action behaves like braking will prevent the output voltage from exceeding the regulated value too much. ovp and non - latched disable on inv pin to prevent the over voltage on the output capacitor from the fault condition, the BW6562A is implemented with a d ynamic ovp function on inv pin. if the output voltage increases despite the b raking and the current entering the inv pin is higher than the i ovp threshold current 27 a, the ovp (dynamic ovp) is triggered and the output gate drive circuit will be shutdown simultaneously thus to stop the switching of the power mosfet . this ovp condit ion is maintained until the inv pin current falls below 7 a to re - enable the internal starter and start switching again. the output change that is able to trigger the dynamic type protection. the inv pin also provides additional function as a non - latched ic d isable. a voltage bel ow 0.2v shuts down the ic and reduces its consumption below 1.7ma. to re - start the ic, the voltage on this pin must exceed 0.45v. the main usage of this function is a remote on/off control input that can be driven by a pwm controller for power management p urposes. however, it also offers a certain degree of additional safety since it will cause the ic to shutdown in case lower resistor of the output divider is shorted to ground or if the upper resistor is missing or fails open. z ero c urrent d etection the z ero current detection block switches on the external mosfet as the current through the boost inductor has gone to zero using an auxiliary winding coupled with the inductor. this feature allows transition - mode operation. if the voltage of the zcd pin goes h igher than 1.4v, the zcd comparator waits until the voltage goes below 0.7v. if the voltage goes below
BW6562A high pfc led driver ?2012 bruckewell techn ology corp., ltd. 9 www.bruckewell - semi.com/ ovp is calculate by v o (27 - 7) r 3 (19) an important advantage of this technique is that the over voltage level can be set independently from the regulated output voltage ; the latter depends on the ratio of r3 to r4, the former on the individual value of r3 . another advantage is the precision beca us e the tolerance of the detection current is about 12%, i.e. 12% tolerance on v o . since v o << v o , the tolerance on the absolute value will be proportionally reduced. w hen the loading of pfc pre - regulator becomes very low, the output voltage tends to stay steadily above the nominal value, which is not the case tha t ovp is trigger ed by abrupt voltage increase. if this situation happens, the error amplifier output will saturate low , hence , when this is detected , the external power transistor is switch ed off, and the ic is put in an idle state ( s tatic ovp). normal ope ration is resumed as the error amplifier goes back into its linear region. as a result, the device will work in burst - mode, with a repeti ti on rate that can be very low. when either ovp is activated, the quiescent co n sumption of the ic is reduced to minimum by the discharge of the v cc capacitor and increase the hold - up capability of the ic supply . the ovp function in the BW6562A is an auto - recovery 0.7v, the zero current detection turns on the mosfet. the zcd pin is protected internally by two clamps, 5.7v upper clamp and 0v lower clamp. the 190 s t imer generates a mosfet turn on signal if the driver output has been low for more than 190 s from the falling edge of the driver output. current sensing and leading edge blanking the typical current mode of pfc controller feedbacks the current signal s to close the control loop and achieve regulation. the BW6562A detects the primary mosfet current from the cs pin; this is for the pulse - by - pulse c urrent limit. the maximum voltage threshold of the current sensing pin is set at 1.08v. from above, the mosfet pe ak current can be obtained from below. i pk (20) a 200ns leading edge blanking (leb) time is included in the input of cs pin to prevent the fal se - trigger from the current spike. in the low power application, if the total pulse width of the turn - on spikes is less than 20 0n s and the negative spike on the cs pin doesnt exceed - 0.3v, it could eliminated the rc filter. however, the total pulse width of the turn - on spike is decided by the output power, circuit design and pcb
BW6562A high pfc led driver 2012 bruckewell techn ology corp., ltd. 10 www.bruckewell - semi.com/ layout. it is strongly recommended to adopt a smaller rc filter for higher power application to avoid the cs pin being damaged by the negative turn - on spike. multiplier th e internal multiplier takes two inputs, one from a portion of the instantaneous rectified line voltage (via pin 3 mult) and the other from the output of the e/a (via pin 2 comp), to feed the pwm comparator to determine the exact instant when the mosfet is to be switched off. the output of multiplier would be rectified sinusoid as similar as instantaneous rectified line voltage different only with scaling factor determined by output of e/a. the output is then fed into pwm comparator to compare with current sense clamp voltage v cs (at 1.08v), to switch mosfet off. figure 1 . m ultiplier characteristics the formula governing all param e ters is given by multiplier output : v cs k v mult (v comp 2.5) (21) where k is the multiplier gain. system designer need s to calculate r1 and r2, for different input mains circumstances. figure 1 and 2 explain multiplier characteristics and v cs clamps vs. t j respectivel y. output drive stage an output stage of a push - pull buffer, with typical + 800ma/ - 600ma driving capability is incorporated to drive a power mosfet directly. the output voltage is clamped at 12v to protect the mosfet gate even when the v cc voltage is highe r than 12v. figure 2. v cs clamps vs. t j
BW6562A high pfc led driver ?2012 bruckewell techn ology corp., ltd. 11 www.bruckewell - semi.com/ example applications single stage led driver with pfc one of major appli c ation s of the BW6562A is to provide a single stage power module with high pf for led lighting. the following circuit, f igure 4 , shows a simplified fly - back ac - dc converter with both constant current ( cc ) and constant voltage ( cv ) feedback from output side, to prevent overload and also provide an over - voltage protection facility . this solution uses an isolated feedback with an opt o - coupler and the sq7103 (+2.5v voltage reference and dual op - amps), each one for voltage and current regulation respectively. as led lighting application, the BW6562A offers the following advantages that make this solution an appropriate method against th e traditionally pwm controller, where a good pf value is required : the input capacitance can be reduced to replace bulky and expensive high voltage electrolytic capacitor (as required by regular offline smps) by a small size, cheaper film capacitor tr ansition - mode ensures low turn - on losses in mosfet and higher efficiency can be achieved. lower parts count means lower material cost as well as lower assembly cost for limited space. few details information about this, please refer separate applicatio n note for details. high pf ba t tery charger the single stage pfc can also be adopted as battery charger. f igure 5 presents an off - line universal mains battery charger that can drive up to 30w . this solution also uses an isolated feedback with an opto - co upler and the bw 7103. to use the BW6562A ic in a lead - acid b attery c harger c ircuit with high pfc, the dc o utput v oltage and the maximum permissible dc o utput c harging c urrent needs to be decided on the basis of the specific battery to be charged. for the l ead - a cid b atteries of different nominal voltages, the fixed constant - voltage, current limited, charging mode, the typical voltage level suggested by most lead - acid battery manufactures are as follows : nominal suggested charging voltage b attery discharge d 6 v 6.9 v 5.25 v 12 v 13.8 v 10.50 v 24 v 27.6 v 21.00 v 48 v 55.2 v 42.00 v t he maximum lead - acid battery charging current is decided by the battery amp - hour capacity, represented as 'c' . the lead - acid b attery manufacturers in general prefer a low b attery c harging c urrent set at c/20 a mp for slow - charging, for improved life of the b attery. h owever, in case of ?ast - charging and if permitted by the b attery manufacturer, the maximum b attery c harging c urrent can be set at c/10 am p. a charge - deple ted battery w ill initially draw the maximum charging current. as the battery gradually gets charged, the c harging c urrent will gradually reduce . the maximum current limit therefore helps avoid a battery getting over - heated during charging and thus avoid damage to the battery. it is advisable to avoid deep discharge of the lead - acid battery, to increase the usable battery life. the secondary side feedback network for the required cv - cc characteristics will therefore be tailored accordingly in the applicat ion circuit. the advanced battery chargers take into account the battery temperature while charging the battery and include appropriate compensation for the same, which is not in the scope of this document. pfc pre - regulator major appli c ation of the bw656 2a is to implement a wide - range mains input pfc pre - regulator, which will be acting the input stage for the cascaded isolation dc - dc converter, and can deliver above 350w in general. typical application circuit diagram is showed on page 1. there are two me thods; in general, to design pre - regulator stage, one is with fixed frequency while the other is with fixed on time. the BW6562A can be implemented by fixed on time due to its simplicity and less expensive, while the fixed frequency technique is more compl icated and beyond the scope of this application note. in fixed on time mode, the BW6562A is also working in transition mode where the inductor current will be turn on when zero crossing is detected. by using boost switching techniques, a pfc is
BW6562A high pfc led driver ?2012 bruckewell techn ology corp., ltd. 12 www.bruckewell - semi.com/ shape the input current by drawing a quasi - sinusoidal current to be in - phase with the line voltage. a simplified circuit, shown in figure 3, can explain the operation as follows : f igure 3 . zcd p in s ynchronization w ithout a uxiliary w inding t he ac mains voltage is rectified by a diode bridge and delivered to the boost converter which boosts the rectified input voltage to a higher regulated dc bus v o. t he error amplifier compares a portion of the output voltage with an internal reference and generates a signal e rror proportional to the difference between them. t he bandwidth of the internal error amplifier is set to be narrow within 20khz, the output would be a dc value over a given half - cycle. o utput of e/a fed into multiplier, multiplied by portion of the rectif ied mains voltage, will generate a scaled rectified sinusoid whose peak amplitude depends on the rectified mains peak voltage as well as the value of error signal. t he output of the multiplier is fed into the non - inverting pin of the internal pwm comparat or. a s the output from multiplier, a sinusoidal reference for pwm, equals to the voltage on the current sense cs pin (#4), the mosfet will be turned off. a s a consequence, the peak inductor current will be enveloped by a rectified sinusoid. a fter the mosfe t is turned off, the boost inductor discharges its stored energy to the load until zero current is detected and turns on mosfet again. i n case there is no auxiliary winding on the boost inductor, a solution can be implemented by simply connecting the zcd pin to the drain of the power mosfet through an rc network as shown in figure 3. in this way the high - frequency edges experienced by the drain will be transferred to the zcd pin, hence arming and triggering the zcd comparator. a lso in this case the resi stance value must be properly chosen to limit the current sourced/sunk by the zcd pin. i n typical applications with output voltages around 400v, recommended values for these components as 22pf (or 33pf) for c zcd and 330 k for r zcd . w ith these values proper operation is ensured even with few volts difference between the regulated output voltage and the peak input voltage.
BW6562A high pfc led driver ?2012 bruckewell techn ology corp., ltd. 13 www.bruckewell - semi.com/ figure 4 . single - stage pfc, constant voltage and constant current figure 5 . high p ower factor ba t tery charger
BW6562A high pfc led driver ?2012 bruckewell techn ology corp., ltd. 14 www.bruckewell - semi.com/ package outline dimensions package type : sop - 8 marking information sop - 8 x = a/t site, yy = year, ww = working week , z = device version BW6562A x yyww z
BW6562A high pfc led driver ?2012 bruckewell techn ology corp., ltd. 15 www.bruckewell - semi.com/ legal disclaimer notice disclaimer all p oduct, p oduct specifications and data a e subject to change without not ice to imp ove eliability, function o design o othe wise. bruckewell technology inc., its affiliates, agents, and employees, and all persons acting on its or their behalf (collectively, bruckewell), disclaim any and all liability for any errors, inacc uracies or incompleteness contained in any datasheet or in any other disclosure relating to any product. bruckewell makes no warranty, representation or guarantee regarding the suitability of the products for any particular purpose or the continuing produc tion of any product. to the maximum extent permitted by applicable law, bruckewell disclaims (i) any and all liability arising out of the application or use of any product. (ii) any and all liability, including without limitation special, consequential or incidental damages. (iii) any and all implied warranties, including warranties of fitness for particular purpose, non - infringement and merchantability. statements regarding the suitability of products for certain types of applications are based on brucke wells knowledge of typical requirements that are often placed on bruckewell products in generic applications. such statements are not binding statements about the suitability of products for a particular application. it is the customers responsibility t o validate that a particular product with the properties described in the product specification is suitable for use in a particular application. parameters provided in datasheets and-or specifications may vary in different applications and performance may vary over time. product specifications do not expand or otherwise modify bruckewells terms and conditions of purchase, including but not limited to the warranty expressed therein.

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